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| 1.2 ghz clock distribution ic, 1.6 ghz inputs, dividers, delay adjust, five outputs ad9512 rev. a information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent ri ghts of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ?2005 analog devices, inc. all rights reserved. features two 1.6 ghz, differential clock inputs 5 programmable dividers, 1 to 32, all integers phase select for output-to-output coarse delay adjust 3 independent 1.2 ghz lvpecl outputs additive output jitter 225 fs rms 2 independent 800 mhz/250 mhz lvds/cmos clock outputs additive output jitter 275 fs rms fine delay adjust on 1 lvds/cmos output serial control port space-saving 48-lead lfcsp applications low jitter, low phase noise clock distribution clocking high speed adcs, dacs, ddss, ddcs, ducs, mxfes high performance wireless transceivers high performance instrumentation broadband infrastructure functional block diagram 05287-001 sync status sync status sclk sdio sdo csb serial control port function syncb, resetb pdb dsync dsyncb detect sync vref rset ad9512 gnd vs clk1 clk1b clk2 clk2b programmable dividers and phase adjust out0 out0b lvpecl /1, /2, /3... /31, /32 out1 out1b lvpecl /1, /2, /3... /31, /32 out2 out2b lvpecl /1, /2, /3... /31, /32 out3 out3b lvds/cmos /1, /2, /3... /31, /32 out4 out4b lvds/cmos /1, /2, /3... /31, /32 delay adjust t figure 1. general description the ad9512 provides a multi-output clock distribution in a design that emphasizes low jitter and low phase noise to maximize data converter performance. other applications with demanding phase noise and jitter requirements can also benefit from this part. there are five independent clock outputs. three outputs are lvpecl (1.2 ghz), and two are selectable as either lvds (800 mhz) or cmos (250 mhz) levels. each output has a programmable divider that may be bypassed or set to divide by any integer up to 32. the phase of one clock output relative to another clock output may be varied by means of a divider phase select function that serves as a coarse timing adjustment. one of the lvds/cmos outputs features a programmable delay element with a range of up to 10 ns of delay. this fine tuning delay block has 5-bit resolution, giving 32 possible delays from which to choose. the ad9512 is ideally suited for data converter clocking applications where maximum converter performance is achieved by encode signals with subpicosecond jitter. the ad9512 is available in a 48-lead lfcsp and can be operated from a single 3.3 v supply. the temperature range is ?40c to +85c.
ad9512 rev. a | page 2 of 48 table of contents specifications ..................................................................................... 4 clock inputs .................................................................................. 4 clock outputs ............................................................................... 4 timing characteristics ................................................................ 5 clock output phase noise .......................................................... 7 clock output additive time jitter ........................................... 10 serial control port ..................................................................... 12 function pin ......................................................................... 13 sync status pin ......................................................................... 13 power ............................................................................................ 14 timing diagrams ............................................................................ 15 absolute maximum ratings .......................................................... 16 thermal characteristics ............................................................ 16 esd caution ................................................................................ 16 pin configuration and function descriptions ........................... 17 ter mi nolo g y .................................................................................... 19 typical performance characteristics ........................................... 20 functional description .................................................................. 24 overall .......................................................................................... 24 function pin ......................................................................... 24 resetb: 58h<6:5> = 00b (default) ..................................... 24 syncb: 58h<6:5> = 01b ....................................................... 24 pdb: 58h<6:5> = 11b ............................................................. 24 dsync and dsyncb pins ....................................................... 24 clock inputs ................................................................................ 24 dividers ........................................................................................ 25 setting the divide ratio ........................................................ 25 setting the duty cycle ........................................................... 25 divider phase offset .............................................................. 29 delay block .................................................................................. 30 calculating the delay ............................................................. 30 outputs ........................................................................................ 30 power-down modes .................................................................. 31 chip power-down or sleep modepdb ........................... 31 distribution power-down .................................................... 31 individual clock output power-down ............................... 31 individual circuit block power-down ................................ 31 reset modes ................................................................................ 31 power-on resetstart-up conditions when vs is applied ........................................................................... 31 asynchronous reset via the function pin ................... 31 soft reset via the serial port ................................................. 31 single-chip synchronization .................................................... 32 syncbhardware sync ................................................... 32 soft syncregister 58h<2> ............................................... 32 multichip synchronization ....................................................... 32 serial control port ......................................................................... 33 serial control port pin descriptions ....................................... 33 general operation of serial control port ............................... 33 framing a communication cycle with csb ...................... 33 communication cycleinstruction plus data ................. 33 wr ite ........................................................................................ 33 read ......................................................................................... 34 the instruction word (16 bits) ................................................ 34 msb/lsb first transfers ........................................................... 34 register map and description ...................................................... 37 summary table ........................................................................... 37 register map description ......................................................... 39 power supply ................................................................................... 43 power management ................................................................... 43 applications ..................................................................................... 44 using the ad9512 outputs for adc clock applications .... 44 cmos clock distribution ........................................................ 44 ad9512 rev. a | page 3 of 48 lvpecl clock distribution ......................................................45 lvds clock distribution ...........................................................45 power and grounding considerations and power supply rejection .......................................................................................45 outline dimensions ........................................................................46 ordering guide ...........................................................................46 revision history 6/05rev. 0 to rev. a changes to features ..........................................................................1 changes to general description .....................................................1 changes to table 1 ............................................................................4 changes to table 3 ............................................................................5 changes to table 4 ............................................................................7 changes to table 5 and table 6 .....................................................12 changes to table 7 ..........................................................................13 changes to figure 12 and figure 14 to figure 16 .......................21 changes to figure 17 caption .......................................................22 changes to figure 23 ......................................................................23 changes to divider phase offset section ....................................29 changes to chip power-down or sleep modepdb section .31 changes to distribution power-down section...........................31 changes to individual clock output power-down section .....31 changes to individual circuit block power-down section ......31 changes to soft reset via the serial port section .......................31 changes to syncbhardware sync section..........................32 changes to soft sync register 58h<2> section ........................32 changes to multichip synchronization section..........................32 changes to serial control port section .......................................33 changes to serial control port pin descriptions section .........33 changes to general operation of serial control port section .......................................................................33 added framing a communication cycle with csb section ....33 added communication cycleinstruction plus data section.....................................................................................33 changes to write section...............................................................33 changes to read section................................................................34 changes to instruction word (16 bits) section ..........................34 changes to msb/lsb first transfers section..............................34 changes to figure 32 and figure 36 .............................................35 added figure 38; renumbered sequentially...............................36 changes to table 17 ........................................................................37 changes to table 18 ........................................................................39 changes to power supply section.................................................43 changes to power management section......................................43 4/05revision 0: initial version ad9512 rev. a | page 4 of 48 specifications typical (typ) is given for v s = 3.3 v 5%; t a = 25c, r set = 4.12 k, unless otherwise note d. minimum (min) and maximum (max) values are given over full v s and t a (?40c to +85c) variation. clock inputs table 1. parameter min typ max unit test conditions/comments clock inputs (clk1, clk2) 1 input frequency 0 1.6 ghz input sensitivity 150 2 mv p-p jitter performance can be improved with higher slew rates (greater swing). input level 2 3 v p-p larger swings turn on the protection diodes and can degrade jitter performance. input common-mode voltage, v cm 1.5 1.6 1.7 v self-biased; enables ac coupling. input common-mode range, v cmr 1.3 1.8 v with 200 mv p-p signal applied; dc-coupled. input sensitivity, single-ended 150 mv p-p cl k2 ac-coupled; clk2b ac bypassed to rf ground. input resistance 4.0 4.8 5.6 k self-biased. input capacitance 2 pf 1 clk1 and clk2 are electrically identical; each can be used as either differential or single-ended input. 2 with a 50 termination, this is ?12.5 dbm. 3 with a 50 termination, this is +10 dbm. clock outputs table 2. parameter min typ max unit test conditions/comments lvpecl clock outputs termination = 50 to v s ? 2 v out0, out1, out2; differential o utput level 3dh (3eh) (3fh)<3:2> = 10b output frequency 1200 mhz see figure 14 output high voltage (v oh ) v s ? 1.22 v s ? 0.98 v s ? 0.93 v output low voltage (v ol ) v s ? 2.10 v s ? 1.80 v s ? 1.67 v output differential voltage (v od ) 660 810 965 mv lvds clock outputs termination = 100 differential; default out3, out4; differential output level 40h (41h)<2:1> = 01b 3.5 ma termination current output frequency 800 mhz see figure 15 differential output voltage (v od ) 250 360 450 mv delta v od 25 mv output offset voltage (v os ) 1.125 1.23 1.375 v delta v os 25 mv short-circuit current (i sa , i sb ) 14 24 ma output shorted to gnd cmos clock outputs out3, out4 single-ended measurements; b outputs: inverted, termination open output frequency 250 mhz with 5 pf load each output; see figure 16 output voltage high (v oh ) v s ? 0.1 v @ 1 ma load output voltage low (v ol ) 0.1 v @ 1 ma load ad9512 rev. a | page 5 of 48 timing characteristics table 3. parameter min typ max unit test conditions/comments lvpecl termination = 50 to v s ? 2 v output level 3dh (3eh) (3fh)<3:2> = 10b output rise time, t rp 130 180 ps 20% to 80%, measured differentially output fall time, t fp 130 180 ps 80% to 20%, measured differentially propagation delay, t pecl , clk-to-lvpecl out 1 divide = bypass 335 490 635 ps divide = 2 ? 32 375 545 695 ps variation with temperature 0.5 ps/c output skew, lvpecl outputs out1 to out0 on same part, t skp 2 70 100 140 ps out1 to out2 on same part, t skp 2 15 45 80 ps out0 to out2 on same part, t skp 2 45 65 90 ps all lvpecl out across multiple parts, t skp_ab 3 275 ps same lvpecl out across multiple parts, t skp_ab 3 130 ps lvds termination = 100 differential output level 40h (41h) <2:1> = 01b 3.5 ma termination current output rise time, t rl 200 350 ps 20% to 80%, measured differentially output fall time, t fl 210 350 ps 80% to 20%, measured differentially propagation delay, t lvds , clk-to-lvds out 1 delay off on out4 out3 to out4 divide = bypass 0.99 1.33 1.59 ns divide = 2 ? 32 1.04 1.38 1.64 ns variation with temperature 0.9 ps/c output skew, lvds outputs delay off on out4 out3 to out4 on same part, t skv 2 ?85 +270 ps all lvds outs across multiple parts, t skv_ab 3 450 ps same lvds out across multiple parts, t skv_ab 3 325 ps cmos b outputs are inverted; termination = open output rise time, t rc 681 865 ps 20% to 80%; c load = 3 pf output fall time, t fc 646 992 ps 80% to 20%; c load = 3 pf propagation delay, t cmos , clk-to-cmos out 1 delay off on out4 divide = bypass 1.02 1.39 1.71 ns divide = 2 ? 32 1.07 1.44 1.76 ns variation with temperature 1 ps/c output skew, cmos outputs delay off on out4 out3 to out4 on same part, t skc 2 ?140 +145 +300 all cmos out across multiple parts, t skc_ab 3 650 ps same cmos out across multiple parts, t skc_ab 3 500 ps lvpecl-to-lvds out everythin g the same; different logic type output skew, t skp_v 0.74 0.92 1.14 ns lvpecl to lvds on same part lvpecl-to-cmos out everythin g the same; different logic type output skew, t skp_c 0.88 1.14 1.43 ns lvpecl to cmos on same part lvds-to-cmos out everything the same; different logic type output skew, t skv_c 158 353 506 ps lvds to cmos on same part ad9512 rev. a | page 6 of 48 parameter min typ max unit test conditions/comments delay adjust out4; lvds and cmos shortest delay range 4 35h <5:1> 11111b zero scale 0.05 0.36 0.68 ns 36h <5:1> 00000b full scale 0.72 1.12 1.51 ns 36h <5:1> 11111b linearity, dnl 0.5 lsb linearity, inl 0.8 lsb longest delay range 4 35h <5:1> 00000b zero scale 0.20 0.57 0.95 ns 36h <5:1> 00000b full scale 9.0 10.2 11.6 ns 36h <5:1> 11111b linearity, dnl 0.3 lsb linearity, inl 0.6 lsb delay variation with temperature long delay range, 10 ns 5 zero scale 0.35 ps/c full scale ?0.14 ps/c short delay range, 1 ns 5 zero scale 0.51 ps/c full scale 0.67 ps/c 1 the measurements are for clk1. for clk2, add approximately 25 ps. 2 this is the difference between any two s imilar delay paths within a single device op erating at the same voltage and temperatur e. 3 this is the difference between any two s imilar delay paths across multiple devices op erating at the same voltage and temperatu re. 4 incremental delay; does not include propagation delay. 5 all delays between the zero scale and full sc ale can be estimated by linear interpolation. ad9512 rev. a | page 7 of 48 clock output phase noise table 4. parameter min typ max unit test conditions/comments clk1-to-lvpecl additive phase noise clk1 = 622.08 mhz, out = 622.08 mhz input slew rate > 1 v/ns divide ratio = 1 @ 10 hz offset ?125 dbc/hz @ 100 hz offset ?132 dbc/hz @ 1 khz offset ?140 dbc/hz @ 10 khz offset ?148 dbc/hz @ 100 khz offset ?153 dbc/hz >1 mhz offset ?154 dbc/hz clk1 = 622.08 mhz, out = 155.52 mhz divide ratio = 4 @ 10 hz offset ?128 dbc/hz @ 100 hz offset ?140 dbc/hz @ 1 khz offset ?148 dbc/hz @ 10 khz offset ?155 dbc/hz @ 100 khz offset ?161 dbc/hz >1 mhz offset ?161 dbc/hz clk1 = 622.08 mhz, out = 38.88 mhz divide ratio = 16 @ 10 hz offset ?135 dbc/hz @ 100 hz offset ?145 dbc/hz @ 1 khz offset ?158 dbc/hz @ 10 khz offset ?165 dbc/hz @ 100 khz offset ?165 dbc/hz >1 mhz offset ?166 dbc/hz clk1 = 491.52 mhz, out = 61.44 mhz divide ratio = 8 @ 10 hz offset ?131 dbc/hz @ 100 hz offset ?142 dbc/hz @ 1 khz offset ?153 dbc/hz @ 10 khz offset ?160 dbc/hz @ 100 khz offset ?165 dbc/hz >1 mhz offset ?165 dbc/hz clk1 = 491.52 mhz, out = 245.76 mhz divide ratio = 2 @ 10 hz offset ?125 dbc/hz @ 100 hz offset ?132 dbc/hz @ 1 khz offset ?140 dbc/hz @ 10 khz offset ?151 dbc/hz @ 100 khz offset ?157 dbc/hz >1 mhz offset ?158 dbc/hz clk1 = 245.76 mhz, out = 61.44 mhz divide ratio = 4 @ 10 hz offset ?138 dbc/hz @ 100 hz offset ?144 dbc/hz @ 1 khz offset ?154 dbc/hz @ 10 khz offset ?163 dbc/hz @ 100 khz offset ?164 dbc/hz >1 mhz offset ?165 dbc/hz ad9512 rev. a | page 8 of 48 parameter min typ max unit test conditions/comments clk1-to-lvds additive phase noise clk1 = 622.08 mhz, out = 622.08 mhz divide ratio = 1 @ 10 hz offset ?100 dbc/hz @ 100 hz offset ?110 dbc/hz @ 1 khz offset ?118 dbc/hz @ 10 khz offset ?129 dbc/hz @ 100 khz offset ?135 dbc/hz @ 1 mhz offset ?140 dbc/hz >10 mhz offset ?148 dbc/hz clk1 = 622.08 mhz, out = 155.52 mhz divide ratio = 4 @ 10 hz offset ?112 dbc/hz @ 100 hz offset ?122 dbc/hz @ 1 khz offset ?132 dbc/hz @ 10 khz offset ?142 dbc/hz @ 100 khz offset ?148 dbc/hz @ 1 mhz offset ?152 dbc/hz >10 mhz offset ?155 dbc/hz clk1 = 491.52 mhz, out = 245.76 mhz divide ratio = 2 @ 10 hz offset ?108 dbc/hz @ 100 hz offset ?118 dbc/hz @ 1 khz offset ?128 dbc/hz @ 10 khz offset ?138 dbc/hz @ 100 khz offset ?145 dbc/hz @ 1 mhz offset ?148 dbc/hz >10 mhz offset ?154 dbc/hz clk1 = 491.52 mhz, out = 122.88 mhz divide ratio = 4 @ 10 hz offset ?118 dbc/hz @ 100 hz offset ?129 dbc/hz @ 1 khz offset ?136 dbc/hz @ 10 khz offset ?147 dbc/hz @ 100 khz offset ?153 dbc/hz @ 1 mhz offset ?156 dbc/hz >10 mhz offset ?158 dbc/hz clk1 = 245.76 mhz, out = 245.76 mhz divide ratio = 1 @ 10 hz offset ?108 dbc/hz @ 100 hz offset ?118 dbc/hz @ 1 khz offset ?128 dbc/hz @ 10 khz offset ?138 dbc/hz @ 100 khz offset ?145 dbc/hz @ 1 mhz offset ?148 dbc/hz >10 mhz offset ?155 dbc/hz ad9512 rev. a | page 9 of 48 parameter min typ max unit test conditions/comments clk1 = 245.76 mhz, out = 122.88 mhz divide ratio = 2 @ 10 hz offset ?118 dbc/hz @ 100 hz offset ?127 dbc/hz @ 1 khz offset ?137 dbc/hz @ 10 khz offset ?147 dbc/hz @ 100 khz offset ?154 dbc/hz @ 1 mhz offset ?156 dbc/hz >10 mhz offset ?158 dbc/hz clk1-to-cmos additive phase noise clk1 = 245.76 mhz, out = 245.76 mhz divide ratio = 1 @ 10 hz offset ?110 dbc/hz @ 100 hz offset ?121 dbc/hz @ 1 khz offset ?130 dbc/hz @ 10 khz offset ?140 dbc/hz @ 100 khz offset ?145 dbc/hz @ 1 mhz offset ?149 dbc/hz > 10 mhz offset ?156 dbc/hz clk1 = 245.76 mhz, out = 61.44 mhz divide ratio = 4 @ 10 hz offset ?122 dbc/hz @ 100 hz offset ?132 dbc/hz @ 1 khz offset ?143 dbc/hz @ 10 khz offset ?152 dbc/hz @ 100 khz offset ?158 dbc/hz @ 1 mhz offset ?160 dbc/hz >10 mhz offset ?162 dbc/hz clk1 = 78.6432 mhz, out = 78.6432 mhz divide ratio = 1 @ 10 hz offset ?122 dbc/hz @ 100 hz offset ?132 dbc/hz @ 1 khz offset ?140 dbc/hz @ 10 khz offset ?150 dbc/hz @ 100 khz offset ?155 dbc/hz @ 1 mhz offset ?158 dbc/hz >10 mhz offset ?160 dbc/hz clk1 = 78.6432 mhz, out = 39.3216 mhz divide ratio = 2 @ 10 hz offset ?128 dbc/hz @ 100 hz offset ?136 dbc/hz @ 1 khz offset ?146 dbc/hz @ 10 khz offset ?155 dbc/hz @ 100 khz offset ?161 dbc/hz >1 mhz offset ?162 dbc/hz ad9512 rev. a | page 10 of 48 clock output additive time jitter table 5. parameter min typ max unit test conditions/comments lvpecl output additive time jitter clk1 = 622.08 mhz 40 fs rms bw = 12 khz ? 20 mhz (oc-12) any lvpecl (out0 to out2) = 622.08 mhz divide ratio = 1 clk1 = 622.08 mhz 55 fs rms bw = 12 khz ? 20 mhz (oc-3) any lvpecl (out0 to out2) = 155.52 mhz divide ratio = 4 clk1 = 400 mhz 215 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz any lvpecl (out0 to out2) = 100 mhz divide ratio = 4 clk1 = 400 mhz 215 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz any lvpecl (out0 to out2) = 100 mhz divide ratio = 4 other lvpecl = 100 mhz interferer(s) both lvds (out3, out4) = 100 mhz interferer(s) clk1 = 400 mhz 222 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz any lvpecl (out0 to out2) = 100 mhz divide ratio = 4 other lvpecl = 50 mhz interferer(s) both lvds (out3, out4) = 50 mhz interferer(s) clk1 = 400 mhz 225 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz any lvpecl (out0 to out2) = 100 mhz divide ratio = 4 other lvpecl = 50 mhz interferer(s) both cmos (out3, out4) = 50 mhz (b outputs off) interferer(s) clk1 = 400 mhz 225 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz any lvpecl (out0 to out2) = 100 mhz divide ratio = 4 other lvpecl = 50 mhz interferer(s) both cmos (out3, out4) = 50 mhz (b outputs on) interferer(s) lvds output additive time jitter clk1 = 400 mhz 264 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out3) = 100 mhz divide ratio = 4 clk1 = 400 mhz 319 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out4) = 100 mhz divide ratio = 4 clk1 = 400 mhz 395 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out3) = 100 mhz divide ratio = 4 lvds (out4) = 50 mhz interferer(s) all lvpecl = 50 mhz interferer(s) ad9512 rev. a | page 11 of 48 parameter min typ max unit test conditions/comments clk1 = 400 mhz 395 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out4) = 100 mhz divide ratio = 4 lvds (out3) = 50 mhz interferer(s) all lvpecl = 50 mhz interferer(s) clk1 = 400 mhz 367 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out3) = 100 mhz divide ratio = 4 cmos (out4) = 50 mhz (b outputs off) interferer(s) all lvpecl = 50 mhz interferer(s) clk1 = 400 mhz 367 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out4) = 100 mhz divide ratio = 4 cmos (out3) = 50 mhz (b outputs off) interferer(s) all lvpecl = 50 mhz interferer(s) clk1 = 400 mhz 548 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out3) = 100 mhz divide ratio = 4 cmos (out4) = 50 mhz (b outputs on) interferer(s) all lvpecl = 50 mhz interferer(s) clk1 = 400 mhz 548 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz lvds (out4) = 100 mhz divide ratio = 4 cmos (out3) = 50 mhz (b outputs on) interferer(s) all lvpecl = 50 mhz interferer(s) cmos output additive time jitter clk1 = 400 mhz 275 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz both cmos (out3, out4) = 100 mhz (b output on) divide ratio = 4 clk1 = 400 mhz 400 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz cmos (out3) = 100 mhz (b output on) divide ratio = 4 all lvpecl = 50 mhz interferer(s) lvds (out4) = 50 mhz interferer(s) clk1 = 400 mhz 374 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz cmos (out3) = 100 mhz (b output on) divide ratio = 4 all lvpecl = 50 mhz interferer(s) cmos (out4) = 50 mhz (b output off) interferer(s) clk1 = 400 mhz 555 fs rms calculated from snr of adc method; f c = 100 mhz with a in = 170 mhz cmos (out3) = 100 mhz (b output on) divide ratio = 4 all lvpecl = 50 mhz interferer(s) cmos (out4) = 50 mhz (b output on) interferer(s) ad9512 rev. a | page 12 of 48 parameter min typ max unit test conditions/comments delay block additive time jitter 1 incremental additive jitter 1 100 mhz output delay fs = 1 ns (1600 a, 1c) fine adj. 00000 0.61 ps delay fs = 1 ns (1600 a, 1c) fine adj. 11111 0.73 ps delay fs = 2 ns (800 a, 1c) fine adj. 00000 0.71 ps delay fs = 2 ns (800 a, 1c) fine adj. 11111 1.2 ps delay fs = 3 ns (800 a, 4c) fine adj. 00000 0.86 ps delay fs = 3 ns (800 a, 4c) fine adj. 11111 1.8 ps delay fs = 4 ns (400 a, 4c) fine adj. 00000 1.2 ps delay fs = 4 ns (400 a, 4c) fine adj. 11111 2.1 ps delay fs = 5 ns (200 a, 1c) fine adj. 00000 1.3 ps delay fs = 5 ns (200 a, 1c) fine adj. 11111 2.7 ps delay fs = 11 ns (200 a, 4c) fine adj. 00000 2.0 ps delay fs = 11 ns (200 a, 4c) fine adj. 00100 2.8 ps 1 this value is incremental. that is, it is in addition to the jitter of the lvds or cmos output without the delay. to estimate the total jitter, the lvds or cmos output jitter should be added to this value using the root sum of the squares (rss) method. serial control port table 6. parameter min typ max unit test conditions/comments csb, sclk (inputs) csb and sclk have 30 k internal pull-down resistors input logic 1 voltage 2.0 v input logic 0 voltage 0.8 v input logic 1 current 110 a input logic 0 current 1 a input capacitance 2 pf sdio (when input) input logic 1 voltage 2.0 v input logic 0 voltage 0.8 v input logic 1 current 10 na input logic 0 current 10 na input capacitance 2 pf sdio, sdo (outputs) output logic 1 voltage 2.7 v output logic 0 voltage 0.4 v timing clock rate (sclk, 1/t sclk ) 25 mhz pulse width high, t pwh 16 ns pulse width low, t pwl 16 ns sdio to sclk setup, t ds 2 ns sclk to sdio hold, t dh 1 ns sclk to valid sdio and sdo, t dv 6 ns csb to sclk setup and hold, t s , t h 2 ns csb minimum pulse width high, t pwh 3 ns ad9512 rev. a | page 13 of 48 function pin table 7. parameter min typ max unit test conditions/comments input characteristics the function pin has a 30 k internal pull-down resistor. this pin should normally be held high. do not leave nc. logic 1 voltage 2.0 v logic 0 voltage 0.8 v logic 1 current 110 a logic 0 current 1 a capacitance 2 pf reset timing pulse width low 50 ns sync timing pulse width low 1.5 high speed clock cycles high speed clock is clk1 or clk2, whichever is being used for distribution. sync status pin table 8. parameter min typ max unit test conditions/comments output characteristics output voltage high (v oh ) 2.7 v output voltage low (v ol ) 0.4 v ad9512 rev. a | page 14 of 48 power table 9. parameter min typ max unit test conditions/comments power-up default mode power dissipation 550 600 mw power-up default state; does not include power dissipated in output load resistors. no clock. power dissipation 800 mw all outputs on. three lvpecl outputs @ 800 mhz, two cmos out @ 62 mhz (5 pf load). does not include power dissipated in external resistors. 850 mw all outputs on. three lvpecl outputs @ 800 mhz, two cmos out @ 125 mhz (5 pf load). does not include power dissipated in external resistors. full sleep power-down 35 60 mw maximum sleep is entered by setting 0ah<1:0> = 01b and 58h<4> = 1b. this powers off all band gap references. does not include power dissipated in terminations. power-down (pdb) 60 80 mw set function pin for pdb operation by setting 58h<6:5> = 11b. pull pdb low. does not include power dissipated in terminations. power delta clk1, clk2 power-down 10 15 25 mw divider, div 2 ? 32 to bypass 23 27 33 mw for each divider. lvpecl output power-down (pd2, pd3) 50 65 75 mw for each output. does not include dissipation in termination (pd2 only). lvds output power-down 80 92 110 mw for each output. cmos output power-down (static) 56 70 85 mw for each output. static (no clock). cmos output power-down (dynamic) 115 150 190 mw for each cmos output, single-ended. clocking at 62 mhz with 5 pf load. cmos output power-down (dynamic) 125 165 210 mw for each cmos output, single-ended. clocking at 125 mhz with 5 pf load. delay block bypass 20 24 60 mw vs. delay block operation at 1 ns fs with maximum delay; output clocking at 25 mhz. ad9512 rev. a | page 15 of 48 timing diagrams 05287-002 c lk1 t cmos t clk1 t lvds t pecl figure 2. clk1/clk1b to clock output timing, div = 1 mode 05287-064 differential lvpecl 80% 20% t rp t fp figure 3. lvpecl timing, differential 05287-065 differential lvds 80% 20% t rl t fl figure 4. lvds timing, differential 05287-066 single-ended cmos 3pf load 80% 20% t rc t fc figure 5. cmos timing, single-ended, 3 pf load ad9512 rev. a | page 16 of 48 absolute maximum ratings table 10. parameter or pin with respect to min max unit vs gnd ?0.3 +3.6 v dsync/dsyncb gnd ?0.3 v s + 0.3 v rset gnd ?0.3 v s + 0.3 v clk1, clk1b, clk2, clk2b gnd ?0.3 v s + 0.3 v clk1 clk1b ?1.2 +1.2 v clk2 clk2b ?1.2 +1.2 v sclk, sdio, sdo, csb gnd ?0.3 v s + 0.3 v out0, out1, out2, out3, out4 gnd ?0.3 v s + 0.3 v function gnd ?0.3 v s + 0.3 v sync status gnd ?0.3 v s + 0.3 v junction temperature 150 c storage temperature ?65 +150 c lead temperature (10 sec) 300 c stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. exposure to absolute maximum ratings for extended periods may affect device reliability. thermal characteristics thermal resistance 1 48-lead lfcsp ja = 28.5c/w 1 thermal impedance measurements were taken on a 4-layer board in still air, in accordance with eia/jesd51-7. esd caution esd (electrostatic discharge) sensiti ve device. electrostatic charges as hi gh as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although this product features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. ad9512 rev. a | page 17 of 48 pin configuration and fu nction descriptions pin 1 indicator 48 47 46 45 44 43 42 41 40 39 38 vs vs gnd rset vs gnd out0 out0 b vs vs gnd 1 2 3 4 5 6 7 8 9 10 11 12 dsync dsyncb vs vs dnc dnc = do no connec t vs clk2 clk2b vs clk1 clk1b function vs out3 out3b vs vs out4 out4b vs vs out1 out1b vs 36 35 34 33 32 31 30 29 28 27 26 25 13 14 15 16 17 18 19 20 21 22 23 24 status sclk sdio sdo csb vs gnd out2b out2 vs vs gnd 37 gnd ad9512 top view (not to scale) 05287-003 figure 6. 48-lead lfcsp pin configuration note that the exposed paddle on this package is an electrical connection as well as a thermal enhancement. for the device to function properly, the paddle must be attached to ground, gnd. ad9512 rev. a | page 18 of 48 table 11. pin function descriptions pin no. mnemonic description 1 dsync detect sync. used for multichip synchronization. 2 dsyncb detect sync complement. us ed for multichip synchronization. 3, 4, 6, 9, 18, 22, 23, 25, 28, 29, 32, 33, 36, 39, 40, 44, 47, 48 vs power supply (3.3 v). 5 dnc do not connect. 7 clk2 clock input. 8 clk2b complementary clock input. used in conjunction with clk2. 10 clk1 clock input. 11 clk1b complementary clock input. used in conjunction with clk1. 12 function multipurpose input. can be programmed as a re set (resetb), sync (syncb), or power-down (pdb) pin. 13 status output used to monitor the status of multichip synchronization. 14 sclk serial data clock. 15 sdio serial data i/o. 16 sdo serial data output. 17 csb serial port chip select. 19, 24, 37, 38, 43, 46 gnd ground. 20 out2b complementary lvpecl output. 21 out2 lvpecl output. 26 out1b complementary lvpecl output. 27 out1 lvpecl output. 30 out4b complementary lvds/inverted cmos output. out4 includes a delay block. 31 out4 lvds/cmos output. out4 includes a delay block. 34 out3b complementary lvds/inverted cmos output. 35 out3 lvds/cmos output. 41 out0b complementary lvpecl output. 42 out0 lvpecl output. 45 rset current set resistor to ground. nominal value = 4.12 k. note that the exposed paddle on this package is an electrical connection as well as a thermal enhancement. for the device to function properly, the paddle must be attached to ground, gnd. ad9512 rev. a | page 19 of 48 terminology phase jitter and phase noise an ideal sine wave can be thought of as having a continuous and even progression of phase with time from 0 degrees to 360 degrees for each cycle. actual signals, however, display a certain amount of variation from ideal phase progression over time. this phenomenon is called phase jitter. although many causes can contribute to phase jitter, one major cause is random noise, which is characterized statistically as being gaussian (normal) in distribution. this phase jitter leads to a spreading out of the energy of the sine wave in the frequency domain, producing a continuous power spectrum. this power spectrum is usually reported as a series of values whose units are dbc/hz at a given offset in frequency from the sine wave (carrier). the value is a ratio (expressed in db) of the power contained within a 1 hz bandwidth with respect to the power at the carrier frequency. for each measurement, the offset from the carrier frequency is also given. it is meaningful to integrate the total power contained within some interval of offset frequencies (for example, 10 khz to 10 mhz). this is called the integrated phase noise over that frequency offset interval and can be readily related to the time jitter due to the phase noise within that offset frequency interval. phase noise has a detrimental effect on the performance of adcs, dacs, and rf mixers. it lowers the achievable dynamic range of the converters and mixers, although they are affected in somewhat different ways. time jitter phase noise is a frequency domain phenomenon. in the time domain, the same effect is exhibited as time jitter. when observing a sine wave, the time of successive zero crossings is seen to vary. in a square wave, the time jitter is seen as a displacement of the edges from their ideal (regular) times of occurrence. in both cases, the variations in timing from the ideal are the time jitter. since these variations are random in nature, the time jitter is specified in units of seconds root mean square (rms) or 1 sigma of the gaussian distribution. time jitter that occurs on a sampling clock for a dac or an adc decreases the snr and dynamic range of the converter. a sampling clock with the lowest possible jitter provides the highest performance from a given converter. additive phase noise it is the amount of phase noise that is attributable to the device or subsystem being measured. the phase noise of any external oscillators or clock sources has been subtracted. this makes it possible to predict the degree to which the device impacts the total system phase noise when used in conjunction with the various oscillators and clock sources, each of which contribute their own phase noise to the total. in many cases, the phase noise of one element dominates the system phase noise. additive time jitter it is the amount of time jitter that is attributable to the device or subsystem being measured. the time jitter of any external oscillators or clock sources has been subtracted. this makes it possible to predict the degree to which the device will impact the total system time jitter when used in conjunction with the various oscillators and clock sources, each of which contribute their own time jitter to the total. in many cases, the time jitter of the external oscillators and clock sources dominates the system time jitter. ad9512 rev. a | page 20 of 48 typical performance characteristics 05287-080 output frequency (mhz) power (w) 0 800 400 0.3 0.6 0.5 0.4 3 lvpecl (div on) 2 lvds (div on) default ? 3 lvpecl + 2 lvds (div on) 3 lvpecl + 2 lvds (div bypassed) figure 7. power vs. frequencylvpecl, lvds 05287-043 5mhz clk1 (eval board) 3ghz figure 8. clk1 smith chart (evaluation board) 05287-081 output frequency (mhz) power (w) 0 120 100 80 60 40 20 0.4 0.7 0.6 0.5 3 lvpecl + 2 cmos (div on) figure 9. power vs. frequencylvpecl, cmos 05287-044 5mhz clk2 (eval board) 3ghz figure 10. clk2 smith chart (evaluation board) ad9512 rev. a | page 21 of 48 05287-053 vert 500mv/div horiz 500ps/div figure 11. lvpecl differential output @ 800 mhz 05287-054 vert 100mv/div horiz 500ps/div figure 12. lvds differential output @ 800 mhz 05287-055 vert 500mv/div horiz 1ns/div figure 13. cmos single-ended output @ 250 mhz with 10 pf load 05287-056 output frequency (mhz) differential swing (v p-p) 100 1600 1100 600 1.2 1.3 1.4 1.5 1.6 1.7 1.8 figure 14. lvpecl differential output swing vs. frequency 05287-050 output frequency (mhz) differential swing (mv p-p) 100 900 700 500 300 500 750 700 650 600 550 figure 15. lvds differential output swing vs. frequency 05287-047 output frequency (mhz) output (v pk ) 0 600 500 400 300 200 100 0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 2pf 10pf 20pf figure 16. cmos single-ended output swing vs. frequency and load ad9512 rev. a | page 22 of 48 05287-051 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 110 ?130 ?120 ?140 ?150 ?160 figure 17. additive phase noiselvpecl div1, 245.76 mhz distribution section only 05287-048 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 80 ?90 ?110 ?100 ?120 ?130 ?140 ?150 ?160 figure 18. additive phase noiselvds div1, 245.76 mhz 05287-045 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 100 ?110 ?120 ?130 ?140 ?150 ?160 figure 19. additive phase noisecmos div1, 245.76 mhz 05287-052 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 110 ?130 ?120 ?140 ?150 ?160 figure 20. additive phase noiselvpecl div1, 622.08 mhz 05287-049 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ? 80 ?90 ?110 ?100 ?120 ?130 ?140 ?150 ?160 figure 21. additive phase noiselvds div2, 122.88 mhz 05287-046 offset (hz) l(f) (dbc/hz) 10 10m 1m 100k 10k 1k 100 ?170 ?100 ?110 ?120 ?130 ?140 ?150 ?160 figure 22. additive phase noisecmos div4, 61.44 mhz ad9512 rev. a | page 23 of 48 05287-090 sync status sync status sclk sdio sdo csb serial control port function syncb, resetb pdb dsync dsyncb detect sync vref rset ad9512 gnd v s clk1 clk1b clk2 clk2b programmable dividers and phase adjust out0 out0b lvpecl /1, /2, /3... /31, /32 out1 out1b lvpecl /1, /2, /3... /31, /32 out2 out2b lvpecl /1, /2, /3... /31, /32 out3 out3b lvds/cmos /1, /2, /3... /31, /32 out4 out4b lvds/cmos /1, /2, /3... /31, /32 delay adjust t figure 23. functional block diagram showing maximum frequencies ad9512 rev. a | page 24 of 48 functional description overall figure 23 shows a block diagram of the ad9512. the ad9512 accepts inputs on either of two clock inputs (clk1 or clk2). this clock can be divided by any integer value from 1 to 32. the duty cycle and relative phase of the outputs can be selected. there are three lvpecl outputs (out0, out1, out2) and two outputs that can be either lvds or cmos level outputs (out3, out4). out4 can also make use of a variable delay block. the ad9512 provides clock distribution function only; there is no clock clean-up. the jitter of the input clock signal is passed along directly to the distribution section and can dominate at the clock outputs. see figure 24 for the equivalent circuit of clk1 and clk2. 05287-016 v s clock input stage clk clkb 5k 5k 2.5k 2.5k figure 24. clk1, clk2 equivalent input circuit function pin the function pin (pin 12) has three functions that are selected by the value in register 58h<6:5>. there is an internal 30 k pull-down resistor on this pin. resetb: 58h<6:5> = 00b (default) in its default mode, the function pin acts as resetb, which generates an asynchronous reset or hard reset when pulled low. the resulting reset writes the default values into the serial control port buffer registers as well as loading them into the chip control registers. the ad9512 immediately resumes operation according to the default values. when the pin is taken high again, an asynchronous sync is issued (see the syncb: 58h<6:5> = 01b section). syncb: 58h<6:5> = 01b the function pin can be used to cause a synchronization or alignment of phase among the various clock outputs. the synchronization applies only to clock outputs that: ? are not powered down ? the divider is not masked (no sync = 0) ? are not bypassed (bypass = 0) syncb is level and rising edge sensitive. when syncb is low, the set of affected outputs are held in a predetermined state, defined by each dividers start high bit. on a rising edge, the dividers begin after a predefined number of fast clock cycles (fast clock is the selected clock input, clk1 or clk2) as determined by the values in the dividers phase offset bits. the syncb application of the function pin is always active, regardless of whether the pin is also assigned to perform reset or power-down. when the syncb function is selected, the function pin does not act as either resetb or pdb. pdb: 58h<6:5> = 11b the function pin can also be programmed to work as an asynchronous full power-down, pdb. even in this full power- down mode, there is still some residual v s current because some on-chip references continue to operate. in pdb mode, the function pin is active low. the chip remains in a power- down state until pdb is returned to logic high. the chip returns to the settings programmed prior to the power-down. see the chip power-down or sleep modepdb section for more details on what occurs during a pdb initiated power-down. dsync and dsyncb pins the dsync and dsyncb pins (pin 1 and pin 2) are used when the ad9512 is used in a multichip synchronized configuration (see the multichip synchronization section). clock inputs two clock inputs (clk1, clk2) are available for use on the ad9512. clk1 and clk2 can accept inputs up to 1600 mhz. see figure 24 for the clk1 and clk2 equivalent input circuit. the clock inputs are fully differential and self-biased. the signal should be ac-coupled using capacitors. if a single-ended input must be used, this can be accommodated by ac coupling to one side of the differential input only. the other side of the input should be bypassed to a quiet ac ground by a capacitor. the unselected clock input (either clk1 or clk2) should be powered down to eliminate any possibility of unwanted crosstalk between the selected clock input and the unselected clock input. ad9512 rev. a | page 25 of 48 dividers each of the five clock outputs of the ad9512 has its own divider. the divider can be bypassed to get an output at the same frequency as the input (1). when a divider is bypassed, it is powered down to save power. all integer divide ratios from 1 to 32 may be selected. a divide ratio of 1 is selected by bypassing the divider. each divider can be configured for divide ratio, phase, and duty cycle. the phase and duty cycle values that can be selected depend on the divide ratio that is chosen. setting the divide ratio the divide ratio is determined by the values written via the scp to the registers that control each individual output, out0 to out4. these are the even numbered registers beginning at 4ah and going through 52h. each of these registers is divided into bits that control the number of clock cycles the divider output stays high (high_cycles <3:0>) and the number of clock cycles the divider output stays low (low_cycles <7:4>). each value is 4 bits and has the range of 0 to 15. the divide ratio is set by divide ratio = ( high_cycles + 1) + ( low_cycles + 1) example 1: set the divide ratio = 2 high_cycles = 0 low_cycles = 0 divide ratio = (0 + 1) + (0 + 1) = 2 example 2: set divide ratio = 8 high_cycles = 3 low_cycles = 3 divide ratio = (3 + 1) + (3 + 1) = 8 note that a divide ratio of 8 may also be obtained by setting: high_cycles = 2 low_cycles = 4 divide ratio = (2 + 1) + (4 + 1) = 8 although the second set of settings produces the same divide ratio, the resulting duty cycle is not the same. setting the duty cycle the duty cycle and the divide ratio are related. different divide ratios have different duty cycle options. for example, if divide ratio = 2, the only duty cycle possible is 50%. if the divide ratio = 4, the duty cycle can be 25%, 50%, or 75%. the duty cycle is set by duty cycle = ( high_cycles + 1)/[( high_cycles + 1) + ( low_cycles + 1)] see table 12 for the values of the available duty cycles for each divide ratio. table 12. duty cycle and divide ratio 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 2 50 0 0 3 67 0 1 3 33 1 0 4 50 1 1 4 75 0 2 4 25 2 0 5 60 1 2 5 40 2 1 5 80 0 3 5 20 3 0 6 50 2 2 6 67 1 3 6 33 3 1 6 83 0 4 6 17 4 0 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 7 57 2 3 7 43 3 2 7 71 1 4 7 29 4 1 7 86 0 5 7 14 5 0 8 50 3 3 8 63 2 4 8 38 4 2 8 75 1 5 8 25 5 1 8 88 0 6 8 13 6 0 9 56 3 4 9 44 4 3 ad9512 rev. a | page 26 of 48 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 9 67 2 5 9 33 5 2 9 78 1 6 9 22 6 1 9 89 0 7 9 11 7 0 10 50 4 4 10 60 3 5 10 40 5 3 10 70 2 6 10 30 6 2 10 80 1 7 10 20 7 1 10 90 0 8 10 10 8 0 11 55 4 5 11 45 5 4 11 64 3 6 11 36 6 3 11 73 2 7 11 27 7 2 11 82 1 8 11 18 8 1 11 91 0 9 11 9 9 0 12 50 5 5 12 58 4 6 12 42 6 4 12 67 3 7 12 33 7 3 12 75 2 8 12 25 8 2 12 83 1 9 12 17 9 1 12 92 0 a 12 8 a 0 13 54 5 6 13 46 6 5 13 62 4 7 13 38 7 4 13 69 3 8 13 31 8 3 13 77 2 9 13 23 9 2 13 85 1 a 13 15 a 1 13 92 0 b 13 8 b 0 14 50 6 6 14 57 5 7 14 43 7 5 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 14 64 4 8 14 36 8 4 14 71 3 9 14 29 9 3 14 79 2 a 14 21 a 2 14 86 1 b 14 14 b 1 14 93 0 c 14 7 c 0 15 53 6 7 15 47 7 6 15 60 5 8 15 40 8 5 15 67 4 9 15 33 9 4 15 73 3 a 15 27 a 3 15 80 2 b 15 20 b 2 15 87 1 c 15 13 c 1 15 93 0 d 15 7 d 0 16 50 7 7 16 56 6 8 16 44 8 6 16 63 5 9 16 38 9 5 16 69 4 a 16 31 a 4 16 75 3 b 16 25 b 3 16 81 2 c 16 19 c 2 16 88 1 d 16 13 d 1 16 94 0 e 16 6 e 0 17 53 7 8 17 47 8 7 17 59 6 9 17 41 9 6 17 65 5 a 17 35 a 5 17 71 4 b 17 29 b 4 17 76 3 c 17 24 c 3 17 82 2 d 17 18 d 2 ad9512 rev. a | page 27 of 48 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 17 88 1 e 17 12 e 1 17 94 0 f 17 6 f 0 18 50 8 8 18 56 7 9 18 44 9 7 18 61 6 a 18 39 a 6 18 67 5 b 18 33 b 5 18 72 4 c 18 28 c 4 18 78 3 d 18 22 d 3 18 83 2 e 18 17 e 2 18 89 1 f 18 11 f 1 19 53 8 9 19 47 9 8 19 58 7 a 19 42 a 7 19 63 6 b 19 37 b 6 19 68 5 c 19 32 c 5 19 74 4 d 19 26 d 4 19 79 3 e 19 21 e 3 19 84 2 f 19 16 f 2 20 50 9 9 20 55 8 a 20 45 a 8 20 60 7 b 20 40 b 7 20 65 6 c 20 35 c 6 20 70 5 d 20 30 d 5 20 75 4 e 20 25 e 4 20 80 3 f 20 20 f 3 21 52 9 a 21 48 a 9 21 57 8 b 21 43 b 8 21 62 7 c 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 21 38 c 7 21 67 6 d 21 33 d 6 21 71 5 e 21 29 e 5 21 76 4 f 21 24 f 4 22 50 a a 22 55 9 b 22 45 b 9 22 59 8 c 22 41 c 8 22 64 7 d 22 36 d 7 22 68 6 e 22 32 e 6 22 73 5 f 22 27 f 5 23 52 a b 23 48 b a 23 57 9 c 23 43 c 9 23 61 8 d 23 39 d 8 23 65 7 e 23 35 e 7 23 70 6 f 23 30 f 6 24 50 b b 24 54 a c 24 46 c a 24 58 9 d 24 42 d 9 24 63 8 e 24 38 e 8 24 67 7 f 24 33 f 7 25 52 b c 25 48 c b 25 56 a d 25 44 d a 25 60 9 e 25 40 e 9 25 64 8 f 25 36 f 8 26 50 c c 26 54 b d 26 46 d b 26 58 a e 26 42 e a 26 62 9 f ad9512 rev. a | page 28 of 48 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 26 38 f 9 27 52 c d 27 48 d c 27 56 b e 27 44 e b 27 59 a f 27 41 f a 28 50 d d 28 54 c e 28 46 e c 28 57 b f 28 43 f b 4ah to 52h divide ratio duty cycle (%) lo<7:4> hi<3:0> 29 52 d e 29 48 e d 29 55 c f 29 45 f c 30 50 e e 30 53 d f 30 47 f d 31 52 e f 31 48 f e 32 50 f f ad9512 rev. a | page 29 of 48 divider phase offset the phase of each output may be selected, depending on the divide ratio chosen. this is selected by writing the appropriate values to the registers, which set the phase and start high/low bit for each output. these are the odd numbered registers from 4bh to 53h. each divider has a 4-bit phase offset <3:0> and a start high or low bit <4>. following a sync pulse, the phase offset word determines how many fast clock (clk1 or clk2) cycles to wait before initiating a clock output edge. the start h/l bit determines if the divider output starts low or high. by giving each divider a different phase offset, output-to-output delays can be set in increments of the fast clock period, t clk . figure 25 shows three dividers, each set for div = 4, 50% duty cycle. by incrementing the phase offset from 0 to 2, each output is offset from the initial edge by a multiple of t clk . 05287-091 123456789101112131415 0 clock input clk divider outputs div = 4, duty = 50% start = 0, phase = 0 start = 0, phase = 1 start = 0, phase = 2 t clk t clk 2 t clk figure 25. phase offsetall dividers set for div = 4, phase set from 0 to 2 for example: clk1 = 491.52 mhz t clk1 = 1/491.52 = 2.0345 ns for div = 4 phase offset 0 = 0 ns phase offset 1 = 2.0345 ns phase offset 2 = 4.069 ns the three outputs may also be described as: out1 = 0 out2 = 90 out3 = 180 setting the phase offset to phase = 4 results in the same relative phase as the first channel, phase = 0 or 360. in general, by combining the 4-bit phase offset and the start h/l bit, there are 32 possible phase offset states (see table 13 ). table 13. phase offsetstart h/l bit 4bh to 53h phase offset fast clock rising edges phase offset 3:0 start h/l 4 0 0 0 1 1 0 2 2 0 3 3 0 4 4 0 5 5 0 6 6 0 7 7 0 8 8 0 9 9 0 10 10 0 11 11 0 12 12 0 13 13 0 14 14 0 15 15 0 16 0 1 17 1 1 18 2 1 19 3 1 20 4 1 21 5 1 22 6 1 23 7 1 24 8 1 25 9 1 26 10 1 27 11 1 28 12 1 29 13 1 30 14 1 31 15 1 the resolution of the phase offset is set by the fast clock period (t clk ) at clk1 or clk2. as a result, every divide ratio does not have 32 unique phase offsets available. for any divide ratio, the number of unique phase offsets is numerically equal to the divide ratio (see table 13 ): div = 4 unique phase offsets are phase = 0, 1, 2, 3 div= 7 unique phase offsets are phase = 0, 1, 2, 3, 4, 5, 6 ad9512 rev. a | page 30 of 48 div = 18 unique phase offsets are phase = 0, 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13, 14, 15, 16, 17 phase offsets may be related to degrees by calculating the phase step for a particular divide ratio: phase step = 360/( divide ratio ) = 360/ div using some of the same examples, div = 4 phase step = 360/4 = 90 unique phase offsets in degrees are phase = 0, 90, 180, 270 div = 7 phase step = 360/7 = 51.43 unique phase offsets in degrees are phase = 0, 51.43, 102.86, 154.29, 205.71, 257.15, 308.57 delay block out4 (lvds/cmos) includes an analog delay element that can be programmed (register 34h to register 36h) to give variable time delays (t) in the clock signal passing through that output. 05287-092 t fine delay adjust (32 steps) full-scale: 1ns to 10ns out4 only clock input n ?select mux lvds cmos output driver figure 26. analog delay (out4) the amount of delay that can be used is determined by the frequency of the clock being delayed. the amount of delay can approach one-half cycle of the clock period. for example, for a 10 mhz clock, the delay can extend to the full 10 ns maximum of which the delay element is capable. however, for a 100 mhz clock (with 50% duty cycle), the maximum delay is less than 5 ns (or half of the period). out4 allows a full-scale delay in the range 1 ns to 10 ns. the full-scale delay is selected by choosing a combination of ramp current and the number of capacitors by writing the appropriate values into register 35h. there are 32 fine delay settings for each full scale, set by register 36h. this path adds some jitter greater than that specified for the nondelay outputs. this means that the delay function should be used primarily for clocking digital chips, such as fpga, asic, duc, and ddc, rather than for data converters. the jitter is higher for long full scales (~10 ns). this is because the delay block uses a ramp and trip points to create the variable delay. a longer ramp means more noise might be introduced. calculating the delay the following values and equations are used to calculate the delay of the delay block. value of ramp current control bits ( register 35h or register 39h <2:0>) = iramp_bits i ramp (a) = 200 ( iramp_bits + 1) no. of caps = no. of 0s + 1 in ramp control capacitor ( register 35h or register 39h <5:3>), that is, 101 = 1 + 1 = 2; 110 = 2; 100 = 2 + 1 = 3; 001 = 2 + 1 = 3; 111 = 0 + 1 = 1) delay_range (ns) = 200 [( no. of caps + 3)/( i ramp )] 1.3286 () () 6 1 10 16000.34ns 4 ? ? ? ? ? ? ? ? ? +?+= ? ramp ramp i capsofno. i offset delay_full_scale (ns) = delay_range + offset fine_adj = value of delay fine adjust ( register 36h or register 3ah <5:1>), that is, 11111 = 31 delay (ns) = offset + delay_range fine_adj (1/31) outputs the ad9512 offers three different output level choices: lvpecl, lvds, and cmos. out0 to out2 are lvpecl only. out3 and out4 can be selected as either lvds or cmos. each output can be enabled or turned off as needed to save power. the simplified equivalent circuit of the lvpecl outputs is shown in figure 27 . 05287-037 3.3v out outb gnd figure 27. lvpecl output simplified equivalent circuit ad9512 rev. a | page 31 of 48 05287-038 3 .5m a 3 .5m a out outb figure 28. lvds output simplified equivalent circuit power-down modes chip power-down or sleep modepdb the pdb chip power-down turns off most of the functions and currents in the ad9512. when the pdb mode is enabled, a chip power-down is activated by taking the function pin to a logic low level. the chip remains in this power-down state until pdb is brought back to logic high. when woken up, the ad9512 returns to the settings programmed into its registers prior to the power-down, unless the registers are changed by new programming while the pdb mode is active. the pdb power-down mode shuts down the currents on the chip, except the bias current necessary to maintain the lvpecl outputs in a safe shutdown mode. this is needed to protect the lvpecl output circuitry from damage that could be caused by certain termination and load configurations when tri-stated. because this is not a complete power-down, it can be called sleep mode. when the ad9512 is in a pdb power-down or sleep mode, the chip is in the following state: ? all clocks and sync circuits are off. ? all dividers are off. ? all lvds/cmos outputs are off. ? all lvpecl outputs are in safe off mode. ? the serial control port is active, and the chip responds to commands. if the ad9512 clock outputs must be synchronized to each other, a sync (see the single-chip synchronization section) is required when exiting power-down mode. distribution power-down the distribution section can be powered down by writing 1 to register 58h<3>. this turns off the bias to the distribution section. if the lvpecl power-down mode is normal operation <00>, it is possible for a low impedance load on that lvpecl output to draw significant current during this power-down. if the lvpecl power-down mode is set to <11b>, the lvpecl output is not protected from reverse bias and can be damaged under certain termination conditions. individual clock output power-down any of the five clock distribution outputs may be powered down individually by writing to the appropriate registers via the scp. the register map details the individual power-down settings for each output. the lvds/cmos outputs may be powered down, regardless of their output load configuration. the lvpecl outputs have multiple power-down modes (see register 3dh, register 3eh, and register 3fh in table 18 ). these give some flexibility in dealing with various output termination conditions. when the mode is set to <10b>, the lvpecl output is protected from reverse bias to 2 v be + 1 v. if the mode is set to <11b>, the lvpecl output is not protected from reverse bias and can be damaged under certain termination conditions. this setting also affects the operation when the distribution block is powered down with register 58h<3> = 1b (see the distribution power-down section). individual circuit block power-down several of the ad9512 circuit blocks (such as clk1 and clk2) can be powered down individually. this gives flexibility in configuring the part for power savings when all chip functionality is not needed. reset modes the ad9512 has several ways to force the chip into a reset condition. power-on resetstart-up conditions when vs is applied a power-on reset (por) is issued when the vs power supply is turned on. this initializes the chip to the power-on conditions that are determined by the default register settings. these are indicated in the default value column of tabl e 1 7 . asynchronous reset via the function pin as mentioned in the function pin section, a hard reset, resetb: 58h<6:5> = 00b (default) , restores the chip to the default settings. soft reset via the serial port the serial control port allows a soft reset by writing to register 00h<5> = 1b. when this bit is set, the chip executes a soft reset. this restores the default values to the internal registers, except for register 00h itself. this bit is not self-clearing. the bit must be written to 00h<5> = 0b for the operation of the part to continue. ad9512 rev. a | page 32 of 48 single-chip synchronization syncbhardware sync the ad9512 clocks can be synchronized to each other at any time. the outputs of the clocks are forced into a known state with respect to each other and then allowed to continue clocking from that state in synchronicity. before a synchronization is done, the function pin must be set as the input (58h<6:5> = 01b). synchronization is done by forcing the function pin low, creating a syncb signal and then releasing it. see the syncb: 58h<6:5> = 01b secti on for a more detailed description of what happens when the syncb: 58h<6:5> = 01b signal is issued. soft syncregister 58h<2> a soft sync can be issued by means of a bit in register 58h<2>. this soft sync works the same as the syncb, except that the polarity is reversed. a 1 written to this bit forces the clock outputs into a known state with respect to each other. when a 0 is subsequently written to this bit, the clock outputs continue clocking from that state in synchronicity. multichip synchronization the ad9512 provides a means of synchronizing two or more ad9512s. this is not an active synchronization; it requires user monitoring and action. the arrangement of two ad9512s to be synchronized is shown in figure 29 . synchronization of two or more ad9512s requires a fast clock and a slow clock. the fast clock can be up to 1 ghz and can be the clock driving the master ad9512 clk1 input or one of the outputs of the master. the fast clock acts as the input to the distribution section of the slave ad9512 and is connected to its clk1 input. the slow clock is the clock that is synchronized across the two chips. this clock must be no faster than one-fourth of the fast clock, and no greater than 250 mhz. the slow clock is taken from one of the outputs of the master ad9512 and acts as a dsync input to the slave ad9512. one of the outputs of the slave must provide this same frequency back to the dsyncb input of the slave. multichip synchronization is enabled by writing to register 58h<0> = 1b on the slave ad9512. when this bit is set, the status pin becomes the output for the sync signal. a low signal indicates an in-sync condition, and a high indicates an out-of-sync condition. register 58h<1> selects the number of fast clock cycles that are the maximum separation of the slow clock edges that are considered synchronized. when 58h<1> = 0b (default), the slow clock edges must be coincident within 1 to 1.5 high speed clock cycles. if the coincidence of the slow clock edges is closer than this amount, the sync flag stays low. if the coincidence of the slow clock edges is greater than this amount, the sync flag is set high. when register 58h<1> = 1b, the amount of coincidence required is 0.5 fast clock cycles to 1 fast clock cycles. whenever the sync flag is set (high), indicating an out-of-sync condition, a syncb signal applied simultaneously at the function pins of both ad9512s brings the slow clocks into synchronization. 05287-093 ad9512 master fast clock <1ghz slow clock <250mhz ad9512 slave fast clock <1ghz slow clock <250mhz sync detect dsync dsyncb outy outm outn f sync f sync syncstatus function (syncb) function (syncb) syncb clk1 figure 29. multichip synchronization ad9512 rev. a | page 33 of 48 serial control port the ad9512 serial control port is a flexible, synchronous, serial communications port that allows an easy interface with many industry-standard microcontrollers and microprocessors. the ad9512 serial control port is compatible with most synchronous transfer formats, including both the motorola spi? and intel? ssr protocols. the serial control port allows read/write access to all registers that configure the ad9512. single or multiple byte transfers are supported, as well as msb first or lsb first transfer formats. the ad9512 serial control port can be configured for a single bidirectional i/o pin (sdio only) or for two unidirectional i/o pins (sdio/sdo). serial control port pin descriptions sclk (serial clock) is the serial shift clock. this pin is an input. sclk is used to synchronize serial control port reads and writes. write data bits are registered on the rising edge of this clock, and read data bits are registered on the falling edge. this pin is internally pulled down by a 30 k resistor to ground. sdio (serial data input/output) is a dual-purpose pin and acts as either an input only or as both an input/output. the ad9512 defaults to two unidirectional pi ns for i/o, with sdio used as an input and sdo as an output. alternatively, sdio can be used as a bidirectional i/o pin by writing to the sdo enable register at 00h<7> = 1b. sdo (serial data out) is used only in the unidirectional i/o mode (00h<7> = 0b, default) as a separate output pin for reading back data. the ad9512 defaults to this i/o mode. bidirectional i/o mode (using sdio as both input and output) may be enabled by writing to the sdo enable register at 00h<7> = 1b. csb (chip select bar) is an active low control that gates the read and write cycles. when csb is high, sdo and sdio are in a high impedance state. this pin is internally pulled down by a 30 k resistor to ground. it should not be left nc or tied low. see the framing a communication cycle with csb section on the use of the csb in a communication cycle. 05287-094 sclk (pin 14) sdio (pin 15) sdo (pin 16) csb (pin 17) ad9512 serial control port figure 30. serial control port general operation of serial control port framing a communication cycle with csb each communication cycle (a write or a read operation) is gated by the csb line. csb must be brought low to initiate a communication cycle. csb must be brought high at the completion of a communication cycle (see figure 38 ). if csb is not brought high at the end of each write or read cycle (on a byte boundary), the last byte is not loaded into the register buffer. csb stall high is supported in modes where three or fewer bytes of data (plus instruction data) are transferred (w1:w0 must be set to 00, 01, or 10, see tabl e 14 ). in these modes, csb can temporarily return high on any byte boundary, allowing time for the system controller to process the next byte. csb can go high on byte boundaries only and can go high during either part (instruction or data) of the transfer. during this period, the serial control port state machine enters a wait state until all data has been sent. if the system controller decides to abort the transfer before all of the data is sent, the state machine must be reset by either completing the remaining transfer or by returning the csb low for at least one complete sclk cycle (but less than eight sclk cycles). raising the csb on a nonbyte boundary terminates the serial transfer and flushes the buffer. in the streaming mode (w1:w0 = 11b), any number of data bytes can be transferred in a continuous stream. the register address is automatically incremented or decremented (see the msb/lsb first transfers s ection). csb must be raised at the end of the last byte to be transferred, thereby ending the stream mode. communication cycleinstruction plus data there are two parts to a communication cycle with the ad9512. the first writes a 16-bit instruction word into the ad9512, coincident with the first 16 sclk rising edges. the instruction word provides the ad9512 serial control port with information regarding the data transfer, which is the second part of the communication cycle. the instruction word defines whether the upcoming data transfer is a read or a write, the number of bytes in the data transfer, and the starting register address for the first byte of the data transfer. write if the instruction word is for a write operation (i15 = 0b), the second part is the transfer of data into the serial control port buffer of the ad9512. the length of the transfer (1, 2, 3 bytes, or streaming mode) is indicated by two bits (w1:w0) in the instruction byte. csb can be raised after each sequence of eight bits to stall the bus (except after the last byte, where it ends the cycle). when the bus is stalled, the serial transfer resumes when csb is lowered. stalling on nonbyte boundaries resets the serial control port. since data is written into a serial control port buffer area, not directly into the ad9512s actual control registers, an additional operation is needed to transfer the serial control port buffer contents to the actual control registers of the ad9512, thereby causing them to take effect. this update command consists of ad9512 rev. a | page 34 of 48 writing to register 5ah<0> = 1b. this update bit is self-clearing (it is not required to write 0 to it to clear it). since any number of bytes of data can be changed before issuing an update command, the update simultaneously enables all register changes since any previous update. phase offsets or divider synchronization will not become effective until a sync is issued (see the single-chip synchronization secti on). read if the instruction word is for a read operation (i15 = 1b), the next n 8 sclk cycles clock out the data from the address specified in the instruction word, where n is 1 to 4 as determined by w1:w0. the readback data is valid on the falling edge of sclk. the default mode of the ad9512 serial control port is unidirectional mode; therefore, the requested data appears on the sdo pin. it is possible to set the ad9512 to bidirectional mode by writing the sdo enable register at 00h<7> = 1b. in bidirectional mode, the readback data appears on the sdio pin. a readback request reads the data that is in the serial control port buffer area, not the active data in the ad9512s actual control registers. 05287-095 s cl k sdio sdo csb update registers 5ah <0> serial control port register buffers ad9512 core control registers figure 31. relationship between serial control port register buffers and control registers of the ad9512 the ad9512 uses address 00h to address 5ah. although the ad9512 serial control port allows both 8-bit and 16-bit instructions, the 8-bit instruction mode provides access to five address bits (a4 to a0) only, which restricts its use to the address space 00h to 01f. the ad9512 defaults to 16-bit instruction mode on power-up. the 8-bit instruction mode (although defined for this serial control port) is not useful for the ad9512; therefore, it is not discussed further in this data sheet. the instruction word (16 bits) the msb of the instruction word is r/ w , which indicates whether the instruction is a read or a write. the next two bits, w1:w0, indicate the length of the transfer in bytes. the final 13 bits are the addresses (a12:a0) at which to begin the read or write operation. for a write, the instruction word is followed by the number of bytes of data indicated by bits w1:w0, which is interpreted according to table 14 . table 14. byte transfer count w1 w0 bytes to transfer 0 0 1 0 1 2 1 0 3 1 1 4 a12:a0 : these 13 bits select the address within the register map that is written to or read from during the data transfer portion of the communications cycle. the ad9512 does not use all of the 13-bit address space. only bits a6:a0 are needed to cover the range of the 5ah registers used by the ad9512. bits a12:a7 must always be 0b. for multibyte transfers, this address is the starting byte address. in msb first mode, subsequent bytes increment the address. msb/lsb first transfers the ad9512 instruction word and byte data may be msb first or lsb first. the default for the ad9512 is msb first. the lsb first mode may be set by writing 1b to register 00h<6>. this takes effect immediately (because it only affects the operation of the serial control port) and does not require that an update be executed. immediately after the lsb first bit is set, all serial control port operations are changed to lsb first order. when msb first mode is active, the instruction and data bytes must be written from msb to lsb. multibyte data transfers in msb first format start with an instruction byte that includes the register address of the most significant data byte. subsequent data bytes must follow in order from high address to low address. in msb first mode, the serial control port internal address generator decrements for each data byte of the multibyte transfer cycle. when lsb_first = 1b (lsb first), the instruction and data bytes must be written from lsb to msb. multibyte data transfers in lsb first format start with an instruction byte that includes the register address of the least significant data byte followed by multiple data bytes. the serial control port internal byte address generator increments for each byte of the multibyte transfer cycle. the ad9512 serial control port register address decrements from the register address just written toward 0000h for multibyte i/o operations if the msb first mode is active (default). if the lsb first mode is active, the serial control port register address increments from the address just written toward 1fffh for multibyte i/o operations. unused addresses are not skipped during multibyte i/o operations; therefore, it is important to avoid multibyte i/o operations that would include these addresses. ad9512 rev. a | page 35 of 48 table 15. serial control port, 16-bit instruction word, msb first msb lsb i15 i14 i13 i12 i11 i10 i9 i8 i7 i6 i5 i4 i3 i2 i1 i0 r/ w w1 w0 a12 = 0 a11 = 0 a10 = 0 a9 = 0 a8 = 0 a7 = 0 a6 a5 a4 a3 a2 a1 a0 0 5287-019 csb sclk don?t care sdio a12 w0w1 r/w a11 a10 a9 a8 a7 a6 a5 a4 a3 a2 a1 a0 d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 don't care don't care don't care 16-bit instruction header register (n) data register (n ? 1) data figure 32. serial control port writemsb fi rst, 16-bit instruction, 2 bytes of data 05287-020 csb sclk sdio sdo register (n) data 16-bit instruction header register (n ? 1) data register (n ? 2) data register (n ? 3) data a12 w0w1 r/w a11 a10 a9 a8 a7 a6 a5 a4 a3 a2 a1 a0 don't care don't care don't care don't care d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 figure 33. serial control port readmsb first, 16-bit instruction, 4 bytes of data 05287-021 t s don't care don't care w1w0a12a11a10a9a8a7a6a5d4d3d2d1d0 don't care don't care r/w t ds t dh t hi t lo t clk t h csb sclk sdio figure 34. serial control port writemsb firs t, 16-bit instruction, timing measurements 05287-022 data bit n ? 1 data bit n csb scl k sdio sdo t dv figure 35. timing diagram for serial control port register read 0 5287-023 csb sclk don?t care don't care 16-bit instruction header register (n) data register (n + 1) data sdio don't care don't care a0 a1 a2 a3 a4 a5 a6 a7 a8 a9 a10 a11 a12 d1d0r/w w1w0 d2 d3 d4 d5 d6 d7 d0 d1 d2 d3 d4 d5 d6 d7 figure 36. serial control port writelsb first, 16-bit instruction, 2 bytes data ad9512 rev. a | page 36 of 48 05287-040 csb sclk sdio t hi t lo t clk t s t ds t dh t h bi n bi n + 1 figure 37. serial control port timingwrite table 16. serial control port timing parameter description t ds setup time between data and rising edge of sclk t dh hold time between data and rising edge of sclk t clk period of the clock t s setup time between csb and sclk t h hold time between csb and sclk t hi minimum period that sclk should be in a logic high state t lo minimum period that sclk should be in a logic low state 05287-067 csb csb toggle indic a tes cycle complete 16 instruction bits + 8 data bits 16 instruction bits + 8 data bits communication cycle 1 communication cycle 2 timing diagram for two successive communication cycles. note that csb must be toggled high and then low at the completion of a communication cycle. t pwh sclk sdio figure 38. use of csb to define communication cycles ad9512 rev. a | page 37 of 48 register map and description summary table table 17. ad9512 register map addr (hex) parameter bit 7 (msb) bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 (lsb) def. value (hex) notes 00 serial control port configuration sdo inactive (bidirectional mode) lsb first soft reset long instruction not used 10 01 to 33 not used fine delay adjust fine delays bypassed 34 delay bypass 4 not used bypass 01 bypass delay 35 delay full-scale 4 not used ramp capacitor <5:3> ramp current <2:0> 00 max. delay full-scale 36 delay fine adjust 4 not used 5-bit fine delay <5:1> not used 00 min. delay value 37, 38, 39, 3a, 3b, 3c not used outputs 3d lvpecl out0 not used output level <3:2> power-down <1:0> 08 on 3e lvpecl out1 not used output level <3:2> power-down <1:0> 08 on 3f lvpecl out2 not used output level <3:2> power-down <1:0> 08 on 40 lvds_cmos out 3 not used cmos inverted driver on logic select output level <2:1> output power 02 lvds, on 41 lvds_cmos out 4 not used cmos inverted driver on logic select output level <2:1> output power 02 lvds, on 42, 43, 44 not used clk1 and clk2 input receivers 45 clocks select, power-down (pd) options not used clks in pd not used not used clk2 pd clk1 pd select clk in 01 all clocks on, select clk1 46, 47, 48, 49 not used dividers 4a divider 0 low cycles <7:4> high cycles <3:0> 00 divide by 2 4b divider 0 bypass no sync force start h/l phase offset <3:0> 00 phase = 0 4c divider 1 low cycles <7:4> high cycles <3:0> 11 divide by 4 4d divider 1 bypass no sync force start h/l phase offset <3:0> 00 phase = 0 4e divider 2 low cycles <7:4> high cycles <3:0> 33 divide by 8 ad9512 rev. a | page 38 of 48 addr (hex) parameter bit 7 (msb) bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 (lsb) def. value (hex) notes 4f divider 2 bypass no sync force start h/l phase offset <3:0> 00 phase = 0 50 divider 3 low cycles <7:4> high cycles <3:0> 00 divide by 2 51 divider 3 bypass no sync force start h/l phase offset <3:0> 00 phase = 0 52 divider 4 low cycles <7:4> high cycles <3:0> 11 divide by 4 53 divider 4 bypass no sync force start h/l phase offset <3:0> 00 phase = 0 54, 55, 56, 57 not used function 58 function pin and sync not used set function pin pd sync pd all ref sync reg sync select sync enable 00 function pin = resetb 59 not used 5a update registers not used update registers 00 self- clearing bit end ad9512 rev. a | page 39 of 48 register map description table 18 lists the ad9512 control registers by hexadecimal address. a specif ic bit or range of bits within a register is indicated by a ngle brackets. for example, <3> refers to bit 3, while <5:2> refers to the range of bits from bit 5 through bit 2. table 18 describes the functionality of the control registers on a bit-by-bit basis. for a more concise (but less descriptive) table, see table 17 . table 18. ad9512 register descriptions reg. addr. (hex) bit(s) name description serial control port configuration any changes to this register takes effect imme diately. register 5ah<0> update registers does not have to be written. 00 <3:0> not used. 00 <4> long instruction when this bit is set (1), the in struction phase is 16 bits. when clear (0), the instruction phase is 8 bits. the default, and only, mode for this part is long instruction (default = 1b). 00 <5> soft reset when this bit is set (1), the chip executes a soft reset, restoring default values to the internal registers, except for this register, 00h. this bit is not self-clearing. a clear (0) has to be written to it in order to clear it. 00 <6> lsb first when this bit is set (1), the inpu t and output data is oriented as lsb first. additionally, register addressing increments. if this bit is clear (0), data is oriented as msb first and register addressing decrements. (default = 0b, msb first.) 00 <7> sdo inactive (bidirectional mode) when set (1), the sdo pin is tri-state and all read data goes to the sdio pin. when clear (0), the sdo is active (unidirectional mode). (default = 0b). not used 01 to 33 <7:0> not used. fine delay adjust 34 <0> delay control out4 delay block control bit. bypasses delay block and powers it down (default = 1b). 34 <7:1> not used. 35 <2:0> ramp current out4 the slowest ramp (200 s) sets the long est full scale of approximately 10 ns. <2> <1> <0> ramp current (s) 0 0 0 200 0 0 1 400 0 1 0 600 0 1 1 800 1 0 0 1000 1 0 1 1200 1 1 0 1400 1 1 1 1600 35 <5:3> ramp capacitor out4 selects the number of capacitors in ramp generation circuit. more capacitors => slower ramp. <5> <4> <3> number of capacitors 0 0 0 4 (default) 0 0 1 3 0 1 0 3 0 1 1 2 1 0 0 3 1 0 1 2 1 1 0 2 1 1 1 1 35 <7:6> not used. 36 <0> not used. ad9512 rev. a | page 40 of 48 reg. addr. (hex) bit(s) name description 36 <5:1> delay fine adjust out4 sets delay within full scale of the ramp; there are 32 steps. 00000b => zero delay (default). 11111b => maximum delay. 36 <7:6> not used. 37 (38) (39) (3a) (3b) (3c) <7:0> not used. outputs 3d (3e) (3f) <1:0> power-down lvpecl out0 (out1) (out2) mode <1> <0> description output on 0 0 normal operation. on pd1 0 1 test onlydo not use. off pd2 1 0 safe power-down. partial power-down; use if output has load resistors. off pd3 1 1 total power-down. use only if output has no load resistors. off output single-ended voltag e levels for lvpecl outputs. 3d (3e) (3f) <3:2> output level lvpecl out0 (out1) (out2) <3> <2> output voltage (mv) 0 0 490 0 1 330 1 0 805 (default) 1 1 650 3d (3e) (3f) <7:4> not used. 40 (41) <0> power-down lvds/cmos out3 (out4) power-down bit for both output and lvds driver. 0 = lvds/cmos on (default). 1 = lvds/cmos power-down. 40 (41) <2:1> output current level lvds out3 (out4) <2> <1> current (ma) termination () 0 0 1.75 100 0 1 3.5 (default) 100 1 0 5.25 50 1 1 7 50 40 (41) <3> lvds/cmos select out3 (out4) 0 = lvds (default). 1 = cmos. 40 (41) <4> inverted cmos driver out3 (out4) affects output only when in cmos mode. 0 = disable inverted cmos driver (default). 1 = enable inverted cmos driver. 40 (41) <7:5> not used. ad9512 rev. a | page 41 of 48 reg. addr. (hex) bit(s) name description clk1 and clk2 45 <0> clock select 0: clk2 drives distribution section. 1: clk1 drives distribution section (default). 45 <1> clk1 power-down 1 = clk1 input is powered down (default = 0b). 45 <2> clk2 power-down 1 = clk2 input is powered down (default = 0b). 45 <4:3> not used. 45 <5> all clock inputs power- down 1 = power-down clk1 and clk2 inputs and a ssociated bias and internal clock tree; (default = 0b). 45 <7:6> not used. 46 (47) (48) (49) <7:0> not used. dividers <3:0> divider high number of clock cycles divider output stays high. 4a out0 (4c) (out1) (4e) (out2) (50) (out3) (52) (out4) <7:4> divider low number of clock cycles divider output stays low. 4a out0 (4c) (out1) (4e) (out2) (50) (out3) (52) (out4) <3:0> phase offset phase offset (default = 0000b). 4b out0 (4d) (out1) (4f) (out2) (51) (out3) (53) (out4) <4> start selects start high or start low. 4b out0 (default = 0b). (4d) (out1) (4f) (out2) (51) (out3) (53) (out4) <5> force forces individual outp uts to the state specified in start (above). this function requires that nosync (below) also be set (default = 0b). 4b out0 (4d) (out1) (4f) (out2) (51) (out3) (53) (out4) <6> nosync ignore chip-level sync signal (default = 0b). 4b out0 (4d) (out1) (4f) (out2) (51) (out3) (53) (out4) ad9512 rev. a | page 42 of 48 reg. addr. (hex) bit(s) name description <7> bypass divider bypass and power-down divider logic; route clock directly to output (default = 0b). 4b out0 (4d) (out1) (4f) (out2) (51) (out3) (53) (out4) 54 (55) (56) (57) <7:0> not used. function 58 <0> sync detect enable 1 = enable sync detect (default = 0b). 58 <1> sync select 1 = raise flag if slow clocks are out-of-s ync by 0.5 to 1 high speed clock cycles. 0 (default) = raise flag if slow clocks are o ut-of-sync by 1 to 1.5 high speed clock cycles. 58 <2> soft sync soft sync bit works the same as the function pi n when in syncb mode, except that this bits polarity is reversed. that is, a high level forces selected outputs into a known state, and a high > low transition triggers a sync (default = 0b). 58 <3> dist ref power-down 1 = power-down the references for the distribution section (default = 0b). 58 <4> sync power-down 1 = power-down the sync (default = 0b). <6> <5> function 0 0 resetb (default) 0 1 syncb 1 0 test only; do not use 58 <6:5> function pin select 1 1 pdb 58 <7> not used. 59 <7:0> not used. 5a <0> update registers 1 written to this bit updates all registers and transfers all serial control port register buffer contents to the control registers on the next rising sclk edge. this is a self-clearing bit. 0 does not have to be written to clear it. 5a <7:1> not used. end ad9512 rev. a | page 43 of 48 power supply the ad9512 requires a 3.3 v 5% power supply for v s . the tables in the specifications section give the performance expected from the ad9512 with the power supply voltage within this range. the absolute maximum range of ?0.3 v to +3.6 v, with respect to gnd, must never be exceeded on the vs pin. good engineering practice should be followed in the layout of power supply traces and ground plane of the pcb. the power supply should be bypassed on the pcb with adequate capacitance (>10 f). the ad9512 should be bypassed with adequate capacitors (0.1 f) at all power pins, as close as possible to the part. the layout of the ad9512 evaluation board (ad9512/pcb) is a good example. the ad9512 is a complex part that is programmed for its desired operating configuration by on-chip registers. these registers are not maintained over a shutdown of external power. this means that the registers can lose their programmed values if v s is lost long enough for the internal voltages to collapse. careful bypassing should protect the part from memory loss under normal conditions. nonetheless, it is important that the v s power supply not become intermittent, or the ad9512 risks losing its programming. the internal bias currents of the ad9512 are set by the r set resistors. this resistor should be as close as possible to the value given as conditions in the specifications section (r set = 4.12 k). this is a standard 1% resistor value and should be readily obtainable. the bias currents set by this resistor determine the logic levels and operating conditions of the internal blocks of the ad9512. the performance figures given in the specifications section assume that this specific resistor value is used. the exposed metal paddle on the ad9512 package is an electrical connection, as well as a thermal enhancement. for the device to function properly, the paddle must be properly attached to ground (gnd). the pcb acts as a heat sink for the ad9512; therefore, this gnd connection should provide a good thermal path to a larger dissipation area, such as a ground plane on the pcb. see the layout of the ad9512 evaluation board (ad9512/pcb or ad9512-vco/pcb) for a good example. power management the power usage of the ad9512 can be managed to use only the power required for the functions that are being used. unused features and circuitry can be powered down to save power. the following circuit blocks can be powered down, or are powered down when not selected (see the register map and description section): ? any of the dividers are powered down when bypassed equivalent to divide-by-one. ? the adjustable delay block on out4 is powered down when not selected. ? any output can be powered down. however, lvpecl outputs have both a safe and an off condition. when the lvpecl output is terminated, only the safe shutdown should be used to protect the lvpecl output devices. this still consumes some power. ? the entire distribution section can be powered down when not needed. powering down a functional block does not cause the programming information for that block (in the registers) to be lost. this means that blocks can be powered on and off without otherwise having to reprogram the ad9512. however, synchronization is lost. a sync must be issued to resynchronize (see the single-chip synchronization section). ad9512 rev. a | page 44 of 48 applications using the ad9512 outputs for adc clock applications any high speed analog-to-digital converter (adc) is extremely sensitive to the quality of the sampling clock provided by the user. an adc can be thought of as a sampling mixer; any noise, distortion, or timing jitter on the clock is combined with the desired signal at the a/d output. clock integrity requirements scale with the analog input frequency and resolution, with higher analog input frequency applications at 14-bit resolution being the most stringent. the theoretical snr of an adc is limited by the adc resolution and the jitter on the sampling clock. considering an ideal adc of infinite resolution where the step size and quantization error can be ignored, the available snr can be expressed approximately by ? ? ? ? ? ? ? ? = j ft snr 2 1 log20 where f is the highest analog frequency being digitized, and t j is the rms jitter on the sampling clock. figure 39 shows the required sampling clock jitter as a function of the analog frequency and effective number of bits (enob). 120 100 80 60 40 20 4 6 8 10 12 14 16 18 1 3 10 30 100 05287-024 full-scale sine wave analog input frequency (mhz) snr (db) enob t j = 50fs t j = 0.1ps t j = 1ps t j = 10ps t j = 100ps t j = 1ns snr = 20log 10 1 2 ft j figure 39. enob and snr vs. analog input frequency see application notes an-756 and an-501 on the adi website at www.analog.com . many high performance adcs feature differential clock inputs to simplify the task of providing the required low jitter clock on a noisy pcb. (distributing a single-ended clock on a noisy pcb can result in coupled noise on the sample clock. differential distribution has inherent common-mode rejection, which can provide superior clock performance in a noisy environment.) the ad9512 features both lvpecl and lvds outputs that provide differential clock outputs, which enable clock solutions that maximize converter snr performance. the input requirements of the adc (differential or single-ended, logic level, termination) should be considered when selecting the best clocking/converter solution. cmos clock distribution the ad9512 provides two clock outputs (out3 and out4), which are selectable as either cmos or lvds levels. when selected as cmos, these outputs provide for driving devices requiring cmos level logic at their clock inputs. whenever single-ended cmos clocking is used, some of the following general guidelines should be followed. point-to-point nets should be designed such that a driver has one receiver only on the net, if possible. this allows for simple termination schemes and minimizes ringing due to possible mismatched impedances on the net. series termination at the source is generally required to provide transmission line matching and/or to reduce current transients at the driver. the value of the resistor is dependent on the board design and timing requirements (typically 10 to 100 is used). cmos outputs are limited in terms of the capacitive load or trace length that they can drive. typically, trace lengths less than 3 inches are recommended to preserve signal rise/fall times and preserve signal integrity. 05287-096 10 microstrip gnd 50pf 60.4 1.0 inch cmos figure 40. series termination of cmos output termination at the far end of the pcb trace is a second option. the cmos outputs of the ad9512 do not supply enough current to provide a full voltage swing with a low impedance resistive, far-end termination, as shown in figure 41 . the far- end termination network should match the pcb trace impedance and provide the desired switching point. the reduced signal swing can still meet receiver input requirements in some applications. this can be useful when driving long trace lengths on less critical nets. 05287-097 50 10 out3, out4 selected as cmos v pullup = 3.3v cmos 3pf 100 100 figure 41. cmos output with far-end termination ad9512 rev. a | page 45 of 48 because of the limitations of single-ended cmos clocking, consider using differential outputs when driving high speed signals over long traces. the ad9512 offers both lvpecl and lvds outputs, which are better suited for driving long traces where the inherent noise immunity of differential signaling provides superior performance for clocking converters. lvds clock distribution low voltage differential signaling (lvds) is a second differential output option for the ad9512. lvds uses a current mode output stage with several user-selectable current levels. the normal value (default) for this current is 3.5 ma, which yields 350 mv output swing across a 100 resistor. the lvds outputs meet or exceed all ansi/tia/eia644 specifications. lvpecl clock distribution the low voltage, positive emitter-coupled, logic (lvpecl) outputs of the ad9512 provide the lowest jitter clock signals available from the ad9512. the lvpecl outputs (because they are open emitter) require a dc termination to bias the output transistors. a simplified equivalent circuit in figure 27 shows the lvpecl output stage. a recommended termination circuit for the lvds outputs is shown in figure 44 . 05287-032 3.3v lvds 100 differential (coupled) 3.3v lvds 100 in most applications, a standard lvpecl far-end termination is recommended, as shown in figure 42 . the resistor network is designed to match the transmission line impedance (50 ) and the desired switching threshold (1.3 v). figure 44. lvds output termination 05287-030 3.3v lvpecl 50 50 single-ended (not coupled) 3.3v 3.3v lvpecl 127 127 83 83 v t = v cc ? 1.3v see application note an-586 on the adi website at www.analog.com for more information on lvds. power and grounding considerations and power supply rejection many applications seek high speed and performance under less than ideal operating conditions. in these application circuits, the implementation and construction of the pcb is as important as the circuit design. proper rf techniques must be used for device selection, placement, and routing, as well as for power supply bypassing and grounding to ensure optimum performance. figure 42. lvpecl far-end termination 05287-031 3.3v lvpecl differential (coupled) 3.3v lvpecl 100 0.1nf 0.1nf 200 200 figure 43. lvpecl with parallel transmission line ad9512 rev. a | page 46 of 48 outline dimensions pin 1 indicator top view 6.75 bsc sq 7.00 bsc sq 1 48 12 13 37 36 24 25 5.25 5.10 sq 4.95 0.50 0.40 0.30 0.30 0.23 0.18 0.50 bsc 12 max 0.20 ref 0.80 max 0.65 typ 1.00 0.85 0.80 5.50 ref 0.05 max 0.02 nom 0.60 max 0.60 max pin 1 indicator coplanarity 0.08 seating plane 0.25 min exposed pad (bottom view) compliant to jedec standards mo-220-vkkd-2 figure 45. 48-lead lead frame chip scale package [lfcsp_vq] 7 mm 7 mm body, very thin quad (cp-48-1) dimensions shown in millimeters ordering guide model temperature range package description package option ad9512bcpz 1 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-1 ad9512bcpz-reel7 1 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-1 ad9512/pcb evaluation board without vco, vcxo, or loop filter 1 z = pb-free part. ad9512 rev. a | page 47 of 48 notes ad9512 rev. a | page 48 of 48 notes ? 2005 analog devices, inc. all rights reserved. trademarks and registered trademarks are the prop erty of their respective owners. d05287C0C6/05(a) |
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